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HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
High Speed Current Mode PWM Control IC for Switching Power Supply
ADE-204-028B (Z) Rev.2 Jul. 2002 Description
The HA17384S/H and HA17385H are PWM control switching regulator IC series suitable for highspeed, current-mode switching power supplies. With ICs from this series and a few external parts, a small, low cost flyback-transformer switching power supply can be constructed, which facilitates good line regulation by current mode control. Synchronous operation driven after an external signal can also be easily obtained which offers various applications such as a power supply for monitors small multi-output power supply. The IC series are composed of circuits required for a switching regulator IC. That is a under-voltage lockout (UVL), a high precision reference voltage regulator (5.0 V 2%), a triangular wave oscillator for timing generation, a high-gain error amplifier, and as totem pole output driver circuit which directly drives the gate of power MOSFETs found in main switching devices. In addition, a pulse-by-pulse type, highspeed, current-detection comparator circuit with variable detection level is incorporated which is required for current mode control. The HA17384SPS includes the above basic function circuits. In addition to these basic functions, the H Series incorporates thermal shut-down protection (TSD) and overvoltage protection (OVP) functions, for configuration of switching power supplies that meet the demand for high safety levels. Between the HA17384 and HA17385, only the UVL threshold voltages differ as shown in the product lineup table.(See next page.) This IC is pin compatible with the "3842 family" ICs made by other companies in the electronics industry. However, due to the characteristics of linear ICs, it is not possible to achieve ICs that offer full compatibility in every detail. Therefore, when using one of these ICs to replace another manufacturer's IC, it must be recognized that it has different electrical characteristics, and it is necessary to confirm that there is no problem with the power supply (mounting) set used.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Functions
* Under-voltage lockout system * Reference voltage regulator of 5.0 V 2% * Triangular wave (sawtooth) oscillator * Error amplifier * Totem pole output driver circuit (direct driving for power MOS FETs) * Current-detection comparator circuit for current mode * OVP function (over voltage protection) *
1 1
* TSD function (thermal shut-down protection) * Note: 1. H series only.
* Protect function by zener diode (between power input and GND)
Features
* High-safety UVL circuit is used (Both VIN and Vref are monitored) * High speed operation: Current detection response time: 100 ns Typ Maximum oscillation frequency: 500 kHz * Low standby current: 170 A Typ * Wide range dead band time (Discharge current of timing capacitance is constant 8.4 mA Typ) * Able to drive power MOSFET directly (Absolute maximum rating of output current is 1 A peak) * OVP function (over voltage protection) is included * (Output stops when FB terminal voltage is 7.0 V Typ or higher)
1
* TSD function (thermal shut-down protection) is included * (Output stops when the temperature is 160C Typ or higher)
1
* Zener protection is included (Clamp voltage between VIN and GND is 34 V Typ) * Wide operating temperature range: Operating temperature: -20C to +105C Junction temperature: 150C * Notes: 1. H series only. 2. S series only.
2
Rev.2, Jul. 2002, page 2 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Product Line-up
Package Additional Function TSD (Thermal shutdown protection) -- OVP (Over voltage protection) -- 8.4 7.6 UVL Power Supply Threshold Voltage
DILP8 (DP-8) HA17384SPS HA17384HPS HA17385HPS
SOP8 (FP-8DC) HA17384SRP HA17384HRP HA17385HRP
VTH UVL (V) Typ 16.0
VTL UVL (V) Typ 10.0
Pin Arrangement
COMP FB CS RT/CT
1 2 3 4
8 7 6 5
Vref VIN OUT GND
(Top view)
Pin Function
Pin No. 1 2 3 4 5 6 7 8 Note: Symbol COMP FB CS RT/CT GND OUT VIN Vref Function Error amplifier output pin Inverting input of error amp./OVP input pin Current sensing signal input pin Timing resistance, timing capacitance connect pin Groung pin PWM Pulse output pin Power supply voltage input pin Reference voltage 5V output pin 1 Note
1. Overvoltage protection (OVP) input is usable only for the HA17384H and HA17385H.
Rev.2, Jul. 2002, page 3 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Block Diagram
0.8mA UVL1
COMP 1 H 5V band gap reference regulator UVL2 OVP latch 4Q S 7 TSD sense OR 34V 2R R 1V 160C CS latch VIN 8 Vref
- + EA
6.5V 1 2 Vref (2.5V)
L
VL VH
FB (OVP input)
- OVP +
2
Vref > 4.7V
*1
7.0V
2VF
-
CS 3
NOR OUT Totem pole output circuit 6 OUT
+
CS
R S
3
PWM LOGIC
Vref Oscillator + RT/CT 4 - 1.2V 2.8 V Latch set pulse 5 GND
8.4 mA
Note: 1. Blocks with bold line are not included in HA17384SPS/SRP.
Rev.2, Jul. 2002, page 4 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Absolute Maximum Ratings
Item Supply voltage DC output current Peak output current Error amplifier input voltage COMP terminal input voltage Error output sink current Power dissipation Operating temperature Junction temperature Symbol VIN IO IO PEAK VFB VCOMP IOEA PT Topr Tj Rating 30 0.1 1.0 -0.3 to VIN -0.3 to +7.5 10 680 -20 to +105 125 150 Storage temperature Tstg -55 to +125 -55 to +150 Unit V A A V V mA mW C C C C C 3 4 3 4 1, 2 Note
Notes: 1. For the HA17384HPS and HA17385HPS, This value applies up to Ta = 43C; at temperatures above this, 8.3 mW/C derating should be applied. For the HA17384SPS, This value applies up to Ta = 68C; at temperatures above this, 8.3 mW/C derating should be applied.
800
Power Dissipation PT (mW)
680mW 600 HA17384SPS HA17384HPS, HA17385HPS 400 374mW
200
166mW 43C 68C 105C 120 125C 140 150C 160
0 -20
0
20
40 60 80 100 Ambient Temperature Ta (C)
Rev.2, Jul. 2002, page 5 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Absolute Maximum Ratings (cont.)
Notes: 2. This is the value when the device is mounted on a glass-epoxy substrate (40 mm x 40 mm x 1.6 mm). However, For the HA17384HRP and HA17385HRP, Derating should be performed with 8.3 mW/C in the Ta 43C range if the substrate wiring density is 10%. Derating should be performed with 11.1 mW/C in the Ta 63C range if the substrate wiring density is 30%. For the HA17384SRP, Derating should be performed with 8.3 mW/C in the Ta 68C range if the substrate wiring density is 10%. Derating should be performed with 11.1 mW/C in the Ta 89C range if the substrate wiring density is 10%.
HA17384SRP : -11.1 mW/C (wiring density is 30%) : -8.3 mW/C (wiring density is 10%) HA17384HRP, HA17385HRP : -11.1 mW/C (wiring density is 30%) : -8.3 mW/C (wiring density is 10%)
800
Power Dissipation PT (mW)
680 mW 600 500 mW 400 374 mW 222 mW 200 166 mW 0 -20 43C 20 63C 68C 89C
105C 120
125C 140
150C 160
0
40 60 80 100 Ambient Temperature Ta (C)
3. Applies to the HA17384HPS/HRP and HA17385HPS/HRP. 4. Applies to the HA17384SPS/SRP.
Rev.2, Jul. 2002, page 6 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Electrical Characteristics
(The condition is: Ta = 25C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice) * Reference Part
Symbol Vref Regline Regload los Vref VN Min 4.9 -- -- -30 -- -- Typ 5.0 20 10 -100 80 100 Max 5.1 50 25 -180 -- -- Unit V mV mV mA ppm/C V Test Condition Io = 1 mA 12 V VIN 25 V -1 mA Io -20 mA Vref = 0V Io = -1 mA, -20C Ta 105C 10 Hz fnoise * 10 kHz 1 1 Note
Item Reference output voltage Line regulation Load regulation Output short current Temperature stability Output noise voltage Note:
1. Reference value for design.
*
Triangular Wave Oscillator Part
Symbol fosc Typ fosc Max fosc 1 fosc 2 IsinkCT VTLCT VTHCT VCT Min 47 500 -- -- 7.5 -- -- -- Typ 52 -- 0.5 5.0 8.4 1.2 2.8 1.6 Max 57 -- 2.0 -- 9.3 -- -- -- Unit kHz kHz % % mA V V V VCT = VTHCT - VTLCT 12 V VIN 25 V -20C Ta 105C VCT = 2.0 V 1 1 1 1 Test Condition CT = 3300 pF, RT = 10 k Note
Item Typical oscillating frequency Maximum oscillating frequency Supply voltage dependency of oscillating frequency Temperature dependency of oscillating frequency Discharge current of CT Low level threshold voltage High level threshold voltage Triangular wave amplitude Note:
1. Reference value for design.
Rev.2, Jul. 2002, page 7 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Electrical Characteristics (cont.)
(The condition is: Ta = 25C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice) * Error Amplifire Part / OVP Part
Symbol VFB IIB AVOL BW PSRR IOsink EA IOsource EA VOH EA VOL EA VOVP IFB(OVP) VIN(OVP RES) Min 2.42 -- 65 0.7 60 3.0 -0.5 5.5 -- 6.0 -- 6.0 Typ 2.50 -0.2 90 1.0 70 9.0 -0.8 6.5 0.7 7.0 30 7.0 Max 2.58 -2.0 -- -- -- -- -- 7.5 1.1 8.0 50 8.0 Unit V A dB MHz dB mA mA V V V A V 12 V VIN 25 V VFB = 2.7 V, VCOMP = 1.1 V VFB = 2.3 V, VCOMP = 5.0 V VFB = 2.3 V, RL = 15 k(GND) VFB = 2.7 V, RL = 15 k(Vref) Increase FB terminal voltage VFB = 8.0 V Decreasing VIN after OVP latched 1 1 1 Test Condition VCOMP = 2.5 V VFB = 5.0 V 2.0 V VO 4.0 V Note
Item Non-inverting input voltage Input bias current Open loop voltage gain Unity gain bank width Power supply voltage rejection ratio Output sink current Output source current High level output voltage Low level output voltage OVP latch threshold voltage OVP (FB) terminal input current OVP latch reset VIN voltage Note:
1. These values are not prescribe to the HA17384SPS/SRP because OVP function is not included.
Rev.2, Jul. 2002, page 8 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Electrical Characteristics (cont.)
(The condition is: Ta = 25C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice) * Current Sensing Part
Symbol AVCS VthCS PSRR IBCS tpd Min 2.85 0.9 -- -- 50 Typ 3.00 1.0 70 -2 100 Max 3.15 1.1 -- -10 150 Unit V/V V dB A ns 12 V VIN 25 V VCS = 2 V Time from when VCS becomes 2 V to when output becomes "L" (2 V) 3 2 Test Condition VFB = 0 V Note 1
Item Voltage gain Maximum sensing voltage Power supply voltage rejection ratio Input bias current Current sensing response time
Notes: 1. The gain this case is the ratio of error amplifier output change to the current-sensing threshold voltage change. 2. Reference value for design. 3. Current sensing response time tpd is definded a shown in the figure 1.
Vth VCS
VOUT (PWM) tpd
Figure 1 Definition of Current Sensing Response Time tpd
*
PWM Output Part
Symbol VOL1 VOL2 VOH1 VOH2 VOL STB tr tf Du max Du min Min -- -- 13.0 12.0 -- -- -- 94 -- Typ 0.7 1.5 13.5 13.3 0.8 80 70 96 -- Max 1.5 2.2 -- -- 1.1 150 130 100 0 Unit V V V V V ns ns % % Test Condition losink = 20 mA losink = 200 mA losource = -20 mA losource = -200 mA VIN = 5 V, losink = 1 mA CL = 1000 pF CL = 1000 pF 1 1 Note
Item Output low voltage 1 Output low voltage 2 Output high voltage 1 Output high voltage 2 Output low voltage at standby mode Rise time Fall time Maximum ON duty Minimum ON duty Note:
1. Pulse application test
Rev.2, Jul. 2002, page 9 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Electrical Characteristics (cont.)
(The condition is: Ta = 25C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice) * UVL Part
Symbol VTH UVL VTL UVL VHYS UVL VT Vref Min 14.5 7.6 9.0 6.8 5.0 0.6 Vref UVL threshold voltage 4.3 Typ 16.0 8.4 10.0 7.6 6.0 0.8 4.7 Max 17.5 9.2 11.0 8.4 7.0 1.0 Vref Unit V V V V V V V Voltage is forced toVref terminal Test Condition Turn-ON voltage when VIN is rising Minimum operating voltage after turn-ON VHYS UVL = VTH UVL - VTL UVL Note 1 2 1 2 1 2
Item Threshold voltage for high VIN level Threshold voltage for low VIN level VIN UVL hysteresis voltage
Notes: 1. For the HA17384S/H. 2. For the HA17385H.
* Total Characteristics
Item Operating current Standby current Current of latch Power supply zener voltage Overheat protection starting temperature Notes: 1. 2. 2. 4. Symbol IIN ISTBY ILATCH VINZ TjTSD Min 7.0 120 200 31 -- Typ 10.0 170 270 34 160 Max 13.0 230 340 37 -- Unit mA A A V C Test Condition CL = 1000 pF, VFB = VCS = 0 V Current at start up VFB = 0 V after VFB = VOVP IIN + 2.5 mA 3, 4 1, 2 Note
These values are not prescribe to the HA17384SPS/SRP because OVP function is not included. VIN = 8.5 V in case of the HA17384H. These values are not prescribe to the HA17384SPS/SRP because TSD function is not included. Reference value for design.
Rev.2, Jul. 2002, page 10 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Timing Chart
Signal Name
Power ON IC turn ON Stationary operation Input voltage VIN Pin 7 0V 2V 16 V (8.4 V)
Waveform timing (Outline)
OVP input OVP latched condition 10 V (7.6 V) Power OFF Reset of OVP latch 7.0 V 2V
This voltage is determined by the transformer
UVL1 Internal signal which cannot be externally monitored. Reference voltage Vref Pin 8 UVL2 Internal signal which cannot be externally monitored. Oscillation voltage of triangular wave RT/CT Pin 4 Start up signal Internal signal which cannot be externally monitored. PWM latch setting signal internal signal which cannot be externally monitored. Error amplifier input signal VFB Pin 2
( ) shows the case using HA17385H 0V
5V 0V 4.7 V 4.7 V
0V 2.8 V
0V IC operates and PWM output stops. 0V
1.2 V
Start up latch release
0V 7.0 V typ (OVP input) 0V VCOMP
Error amplifier output signal 0V VCOMP Pin 1 ID *1 OVP latch signal Internal signal which cannot be externally monitored. PWM output voltage VOUT Pin 6
ID
0V VIN 0V
Note: 1. ID indicates the power MOSFET drain current; it is actually observed as voltage VS generated by power MOSFET current detection source resistance RS. VCOMP indicates the error amp output voltage waveform. Current mode operation is performed so that a voltage 1/3 that of VCOMP is the current limiter level.
Rev.2, Jul. 2002, page 11 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Operation (Description of Timing Chart)
From Power ON to Turn On After the power is switched ON, the power supply terminal voltage (VIN) of this IC rises by charging 1 through bleeder resistor RB. At this time, when the power voltage is in the range of 2 V to 16 V* . The low-voltage, lock out UVL1 operates and accordingly the OUT voltage, that is, the gate voltage of the power MOS FET, is fixed at 1.3 V or a lower value, resulting in the power MOS FET remaining in the OFF state. When the power supply voltage reaches 16 V, UVL1 of this IC is reset and the reference voltage (Vref) generating part turns ON. However, until Vref becomes 4.7 V, the low-voltage, lock out UVL2 operates to keep the OUT terminal voltage low. After Vref terminal voltage becomes 4.7 V or higher, OUT terminal outputs a PWM pulse. Note: 1. The value is for the HA17384S/H. The value is 8.4 V for the HA17385H. Generation of Triangular Wave and PWM Pulse After the output of the Vref, each blocks begins to operate. The triangular wave is generated on the RT/CT terminal. For PWM pulses, the triangular wave rise time is taken as the variable on-duty on-time. The triangular wave fall time is taken as the dead-band time. The initial rise of the triangular wave starts from 0 V, and to prevent a large on-duty at this time, the initial PWM pulse is masked and not output. PWM pulses are outputted after the second triangular wave. The above operation is enabled by the charge energy which is charged through the bleeder resistor RB into the capacitor CB of VIN. Stationary Operation PWM pulses are outputted after the second wave of the triangular wave and stationary operation as the switching power supply starts. By switching operation from ON/OFF to OFF/ON in the switching device (power MOS FET), the transformer converts the voltage. The power supply of IC VIN is fed by the back-up winding of the transformer. In the current mode of the IC, the current in the switcing device is always monitored by a source resistor RCS. Then the current limiter level is varied according to the error voltage (COMP terminal voltage) for PWM control. One third of the error voltage level, which is divided by resistors "2R" and "R" in the IC, is used to sense the current (R = 25 k). Two diodes between the error output and the 2R-R circuit act only as a DC level shifter. Actually, these diodes are connected between the 2R-R circuit and GND, and, the current sensing comparator and GND, respectively. Therefore, these blocks operate 1.4 V higher than the GND level. Accordingly, the error of the current sensing level caused by the switching noise on the GND voltage level is eliminated. The zener diode of 1 V symbolically indicates that the maximum sensing voltage level of the CS terminal is 1 V.
Rev.2, Jul. 2002, page 12 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Power OFF At power OFF, the input voltage of the transformer gradually decreases and then VIN of IC also decreases 2 according to the input voltage. When VIN becomes lower than 10 V* or Vref becomes lower than 4.7 V, UVL1 (UVL2) operates again and the PWM pulse stops. Note: 2. The value is for the HA17384S/H. The value is 7.6 V for the HA17385H.
Commercial AC voltage - + - 100 200V RB 220k 1/4W HRP32 P CB 10 50V + - B S
Power switch
Line filter 20k
+ Rectifier bridge diode VIN
SBD ex. HRP24
+
+ - 1000 10V DC output -
OVP input (Ex: from photocoupler)
3.6k
0.1 COMP 150k RT 10k 100p FB CS RT/CT CT 3300p VCS 330p 1k VIN 51 OUT GND Vref
Floating ground
Power MOSFET ex. 2SK1567
HA17384H, HA17385H RCS 1 2W
Figure 2 Mounting Circut Diagram for Operation Expression
Rev.2, Jul. 2002, page 13 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
2R 1V - VCS CS terminal + CS R 2VF CS latch R S VCOMP COMP terminal (Error output)
3
PWM pulse
Latch setting pulse (Implemented in triagular wave oscillator) Latch setting pulse VCOMP Error voltage VCS Current sensing level x13
Figure 3 Operation Diagram of Current Sensing Part
Current Sense Comparator Threshold Voltage VCS (V)
Point: 1) At maximum rated load, the setting should be made to give approximately 90% of area A below. 2) When the OVP latch is operated, the setting should be made in area B or C. 1.0 B Heavy load 0.8 0.6 A 0.4 Light load 0.2 C 0.0 0 1 2 3 4 5 6 7 Error Amplifier Output Voltage Vcomp (V) 8 1.4V 4.4V 7.5V A : Stationary operation / PWM (Current-mode operation) B : Current limit operation / Max duty cycle C : No sensitivity area / No PWM output
Figure 4 Current Sense Characteristics
Rev.2, Jul. 2002, page 14 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Features and Theory of Current Mode Control
Features of Current Mode Control * Switch element current detection is performed every cycle, giving a high feedback response speed. * Operation with a constant transformer winding current gives a highly stable output voltage (with excellent line regulation characteristics, in particular). * Suitable for flyback transformer use. * External synchronous operation is easily achieved. (This feature, for example, is applicable to synchronization with a forizontal synchronizing signal of CRT monitor.) Theory of Current Mode Control In current mode control, a PWM pulse is generated not by comparing an error voltage with a triangular wave voltage in the voltage mode, but by changing the current limiter level in accordance with the error voltage (COMP terminal in this IC, that is,output of the error amplifier output) which is obtained by constantly monitoring the current of the switching device (power MOS FET) using source resistor RCS. One of the features of current mode control is that the current limited operates in all cycles of PWM as described by the above theory. In voltage mode, only one feedback loop is made by an output voltage. In current mode, on the other hand, two loops are used. One is an output voltage loop and the other is a loop of the switching device current itself. The current of the switching device can be controlled switch high speed. In current mode control, the current in the transformer winding is kept constant, resulting in high stability. An important consequence is that the line regulation in terms of total characteristics is better than that in voltage mode.
AC input OSC S Flip flop R RS
Transformar
DC output
Current sense comparator
+ - 2R R
IS VCOMP Error amplifier - + Vref
Figure 5 Block Diagram of Current Mode Switching Power Spply
Rev.2, Jul. 2002, page 15 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
A. Control in the case of heavy load VCS
IS B. Control in the case of light load VCS
IS As the load becomes heavy and the DC output decreases, the current sensing level is raised as shown in A. above in order to increase the current in the switching device in each cycle. When the load decreases, inverse control is carried out as shown in B. above.
Figure 6 Primary Current Control of Transformer in Current Mode (Conceptual Diagram)
Rev.2, Jul. 2002, page 16 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Main Characteristics
Supply Current vs. Supply Voltage (HA17384S/H) 20
Operating Current IIN (mA) Operating Current IIN (mA)
Ta = 25C fosc = 52kHz CT = 3300pF RT = 10k
Supply Current vs. Supply Voltage (HA17385H) 20
Ta = 25C fosc = 52kHz CT = 3300pF RT = 10k
15
15
10
Latch current (HA17384H)
10
5
5
Latch current
0
0
10 20 30 Power supply voltage VIN (V)
40
0
0
10 20 30 Power supply voltage VIN (V)
40
Standby Current/Latch Current vs. Supply Voltage
Exploded diagram of the small current part from the above figure (HA17384S/H)
Standby Current/Latch Current vs. Supply Voltage
Exploded diagram of the small current part from the above figure (HA17385H)
2.0
Ta = 25C
2.0
Operating Current IIN (mA)
1.5
Operating Current IIN (mA)
Ta = 25C
1.5
1.0
Latch current (HA17384H)
1.0
Latch current
0.5
0.5
0
0
10 20 30 Power supply voltage VIN (V)
40
0
0
10 20 30 Power supply voltage VIN (V)
40
Operating Current vs. Ambient Temperature Standby Current/Latch Current vs. Ambient Temperature 12
Standby Latch Current (A) Operating Current IIN (mA)
VIN = 15V fosc = 52kHz CT = 3300pF RT = 10k
400
Latch current VIN = 15V (HA17384H) VIN = 8.5V (HA17385H)
11
300
10
200
9
100
Stanby current
8 -20
0 20 40 60 80 Ambient temperature Ta (C)
105
0 -20
0 20 40 60 80 Ambient temperature Ta (C)
105
Rev.2, Jul. 2002, page 17 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
UVL Threshold Voltage vs. Ambient Temperature 20
HA17384S/H
Line Regulation Characteristics of Reference Voltage 5.2
Reference voltage Vref (V)
Ta = 25C CT = 3300pF VIN = 10V or more (HA17384S/H) RT = 10k VIN = 7.6V or more (HA17385H)
UVL voltage (V)
15
VTH VTL
HA17385H
5.1
10
VTH VTL
5.0
5
4.9
0 -20
4.8 0 20 40 60 Ambient temperature Ta (C) 85 0 10 20 Supply voltage VIN (V) 30
Load Regulation Characteristics of Reference Voltage 6.0
Reference voltage Vref (V) Reference voltage Vref (V)
Ta = 25C VIN = 15V CT = 3300pF RT = 10k
Reference Voltage vs. Ambient Temperature 5.2
VIN = 15V CT = 3300pF RT = 10k
5.5
5.1
5.0
Vref short protection operates
5.0
4.5
4.9
4.0 0
20 40 60 80 100 Output current of Vref terminal (mA)
4.8 -20
0 20 40 60 80 Ambient temperature Ta (C)
105
CT discharge current IsinkCT (mA)
CT Discharge Current vs. RT/CT Terminal Voltage 9.5
CT discharge current ICT (mA)
Ta = 25C VIN = 15V Measured when RT/CT terminal voltage is externally supplied
CT Discharge Current vs. Ambient Temperature 9.5
VIN=15 V
9.0
9.0
8.5
Minimum voltage of triangular wave Maximum voltage of triangular wave
Measured when RT/CT terminal voltage of 2 V is externally supplied
8.5
8.0
8.0
7.5 0 1 2 3 RT/CT terminal voltage VCT (V) 4
7.5 -20
0 20 40 60 80 Ambient temperature Ta (C)
105
Rev.2, Jul. 2002, page 18 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
500
Oscillation frequency fosc (kHz)
200 100 50 20 10 5 500
Ta = 25C VIN = 15V
F 0p 47 = pF CT 00 F 10 00p F 22 00p F 01 F 0. 2 47
02 0.
04 0.
1k 2k
Timing resistance RT ()
Figure 7 Oscillation Frequency vs. Timing Resistance
F 7
5k
10k 20k
50k 100k 200k
Case 1. Setting large maximum duty cycle. Triangular wave
PWM maximum ON pulse Du max = 95% fosc = 52kHz In the case of small CT and large RT (ex. CT = 3300pF, RT = 10k) Case 2. Setting small maximum duty cycle. Triangular wave PWM maximum ON pulse Du max = 40% fosc = 52kHz In the case of large CT and small RT (ex. CT = 0.033F, RT = 680)
Figure 8 Relationship Between Triangular Wave and Maximum ON Duty of PWM Pulse
Rev.2, Jul. 2002, page 19 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
100
Maximum ON duty Du max (%)
75
Ta = 25C VIN = 15V
50
25
0 500
1k
2k
5k
10k
20k
50k
100k 200k
Timing Resistance RT () Note: In the oscillation system of this IC, a constant discharging current of 8.4mA flows the timing capacitor during triangular wave fall. Therefore, note that a small maximum ON duty (large dead band) leads to a large supply current. Refer to the equations of oscillation frequency and supply current for details.
Figure 9 PWM Pulse ON Duty vs. Timing Resistance
Rev.2, Jul. 2002, page 20 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Oscillation Frequency vs. Ambient Temperature 65
Operating Current IIN (mA)
VIN = 15V CL = 1000pF
Oscillation Frequency fosc (kHz)
Operating Current vs. Maximum ON Duty 25
VIN = 15V
60 55 50 45 40 -20
Dumax = 40% CT = 0.033F RT = 680 CT = 3300pF Dumax = 95% RT = 10k
20 15 10 5 0 0
Ta=25C CL = 1000pF VCS = 0V fos VFB = 0V c=3 00 kH z fos c=5 0kH z
0 20 40 60 80 Ambient Temperature Ta (C)
105
25 50 75 100 Maximum ON Duty Du max (%)
Rise/Fall Time of Output Pulse vs. Load Capacitance 250
VIN = 15V VCS = 0V 200 VFB = 0V Ta = 25C CT = 3300pF RT = 10k
Rise/Fall Time of Output Pulse vs. Ambient Temperature 250
VIN = 15V VCS = 0V 200 VFB = 0V CL = 1000pF
Rise/Fall Time (ns)
Rise/Fall Time (ns)
150 100 50 0 0
Ris e e tim
lT
150 100 50 0 -20
Rise time tr
Fall Time tf
CT = 3300pF RT = 10k
tr
Fal
tf ime
1000 4000 2000 3000 Output load capacitance CL (pF)
0 20 40 60 80 Ambient temperature Ta (C)
105
Current Sensing Level vs. Ambient Temperature 1.25
Current sensing level VCS (V)
Relationship Between Low Voltage Malfunction Protection and PWM Output
VIN (UVL1) Vref (UVL2) PWM OUTPUT L L L H L L H H
Available to output
1.00 0.75 0.50 0.25
VIN = 15V Measured when COMP terminal VFB = 0V voltage is externally supplied
L H L
0 -20
IC is in the ON Condition Standby state and Operation Standby description state state output is state fixed to LO.
0 20 40 60 80 Ambient temperature Ta (C)
105
Rev.2, Jul. 2002, page 21 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
100 VIN = 15V, Ta = 25C 75
Gain AVO 25 0 -25
Unit gain frequency fT = 1MHz Typ
0 60
Phase Phase margin at fT O = 60 Typ 100 1k 10k 100k 1M Error Amplifier Input Signal Frequency f (Hz)
120 180 10M
10
Figure 10 Open Loop Gain Characterisrics of Error Amplifier
Rev.2, Jul. 2002, page 22 of 30
Phase (deg)
Gain AVO (dB)
50
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
*Calculation of operation parameters
1. Maximum ON duty Du max (Refer to the right figure.) 1 Du max = 190 1 + 1.78 x In 1 + RT - 440
Triangular wave
(
)
2. Oscillation frequency fosc fosc = CT x RT x 1
{ 0.56 + In (1 + R 190 )} - 440
T
PWM maximum ON pulse
From the above two equations, the following two equations are obtained. 3. Equalization to device RT from Du max RT = e 190 0.56 (1/Du max - 1) + 440 -1
(e = 2.71828.base of natural logarithm)
Dumax is the ratio of maximum ON time of PWM to one cycle time. In the above case, Dumax = 95%
4. Equation to device CT from fosc and RT Du max CT = 1.78 x fosc x RT 5. Operating current IIN IIN = IQ + IsinkCT x (1 - Du max) + Ciss x VIN x fosc
providing that IQ = 8.4mA Typ (Supply current when oscillation in IC stops.) Ciss is the input gate capacitance of the power MOSFET which is connected and VIN is the supply voltage of the IC. Example 1: Calculation when RT = 10k and CT = 3300pF fosc = 52kHz, Du max = 95%, IIN = 9.7mA Example 2: Calculation for 50% of Du max and 200 kHz of fosc RT = 693, CT = 6360pF, IIN = 12.5mA However, Ciss = 1000pF, VIN = 18V Note that the actual value may differ from the calculated one because of the internal delay in operation and input characteristics of the POWER MOS FET. Check the value when mounting. Additionally a small Dumax leads to a large supply current, even if the frequency is not changed, and start up may become difficult. In such a case, the following measure is recommended. (1) For an AC/DC converter, a small bleeder resistance is required. (2) The large capacitance between Vref and GND is required. (3) Use a large Dumax with a triangular wave and raise the current limit of the switching device to around the maximum value (1.0V Typ). V The current limit is expressed as IDmax = THCS RCS
Figure 11 Calculation of Operation Parameters
Rev.2, Jul. 2002, page 23 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Application Circuit Example (1)
Rectifier bridge diode + 141V + - Commercial AC 100V Line filter 20k 3.6k 10k 2SA1029 HA17384H, HA17385H 0.1 COMP 10k RT 10k 150k 100p FB CS RT/CT CT 3300p 470p 1k VIN 51 OUT GND 1k Vref 100 200V 220k 1/4W HRP32 P 10 50V + - B SBD 1000 HRP24 10V + S + - DC 5V, 3A OUTPUT
-
16.4V VIN
-
Transformer specification example EI-22 type core (H7C18 x 06Z) Gap length lg = 0.3mm 2SK1567 Transformer coil example P: 0.580T/570H S: 0.516T Bifiler/22H B: 0.244T/170H 1 2W
47k HA17431
The circuit for output current limiter
Notes: 1. : PRIMARY GND, : SECONDARY GND. 2. Check the wiring direction of the transformer coil. 3. Insert a snubber circuit if necessary. 4. OVP function is not included in HA17384SPS/SRP.
Snubber circuit example 470p 1kV FRD DFG1C8 51 P S
(Opetation Theory) Because this circuit is a flyback type, the voltages in the primary (P), secondary (s) coils of the transformer and backup (B) coil are proportional to each other. Using this, the output voltage of the backup coil (VIN of IC) is controlled at constant 16.4V. (The voltage of the point divided by resistors of 20k and 3.6k is 2.5V).
Figure 12 Primary Voltage Sensing Flyback Converter
Rev.2, Jul. 2002, page 24 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Application Circuit Example (2)
When the error amplifier is used - Rectifier bridge diode + 141V + - Commercial AC 100V 2SA1029 10k 47k HA17431 Line filter 10k VIN 16.4V 10 50V HRP32 P +B - 100 200V 220k 1/4W SBD HRP24 S Transformer specification example EI-22 type core (H7C18 x 06Z) Gap length lg = 0.3mm Transformer coil example P: 0.580T/570H S: 0.516T Bifiler/22H B: 0.244T/170H + 330 3.3 + - 3.3k DC 5V, 3A OUTPUT
+ 1.8k - 1000 10V B 4.7k
The circuit for output current limiter
HA17384H, HA17385H 0.1 Vref VIN OUT GND 1k 1 2W 4.7k
HA17431
-
COMP 150k 100p FB RT 10k CS RT/CT CT 3300p 470p 1k
2SK1567 51
Photocoupler (for output control)
When the error amplifier is not used OVP input Bleeder resistor (adjuster according to the rating of the Photocoupler)
COMP FB CS RT/CT
Vref 0.8mA VIN OUT GND
(Operation Theory) On the secondary side (S) of the flyback converter, error amplification is carried out by a shunt regulator and photocoupler. The voltage of the backup coil (B) is not monitored, which differs from the application example (1). In addition, OVP operates on the secondary side (S) using a photocoupler. Refer to the application example (1) for the other notes.
Figure 13 Secondary Voltage Sensing Flyback Converter
Rev.2, Jul. 2002, page 25 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Application Examples for Fuller Exploitation of Power Supply Functions
A number of application examples are briefly described below. 1. Soft start A soft start is a start method in which the PWM pulse width is gradually increased when the power supply is activated. This prevents the stress on the transformer and switch element caused by a rapid increase in the PWM pulse width, and also prevents overshoot when the secondary-side output voltage rises. The circuit diagram is shown in figure 14.
VIN 7 DIN IO 800A typ FB 2 2.5V (3V) IC internal circuit (around error amp.) 2R R (1V) 1V To power supply detection comparator CST - + EA (4.4V) Vref 5V 8 VREF (5V) D2 (3.7V)
1
RCU COMP D1
External circuit (only partially shown)
Figure 14 Circuit Diagram for Soft Start Operation: In this circuit, error amp output source current IO (800 A typ.) gradually raises the switch element current detection level, using a voltage slope that charges soft start capacitance CST. When the voltage at each node is at the value shown in parentheses in the figure, the soft start ends. The soft start time is thus given by the following formula:
TST = (3.7 V/800 A) x CST 4.62 CST (ms) (CST unit: F)
External parts other than CST operate as follows: Diode D1 Diode D2 : Current detection level shift and current reverse-flow prevention. : Together with diode DIN in the IC, CST charge drawing when power supply falls.
Resistance RCU : For CST charge-up at end of soft start. (Use a high resistance of the order of several hundred k.) Note: During a soft start, since PWM pulses are not output for a while after the IC starts operating, there is a lack of energy during this time, and intermittent mode may be entered. In this case, the capacitance between Vref and GND should be increased to around 4.7 F to 10 F.
Rev.2, Jul. 2002, page 26 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Notice for Use
1. OVP Latch Block * Case When DC power is applied directly as the power supply of the HA17384H, HA17385H, without using the transformer backup coil. Also, when high-frequency noise is superimposed on the VIN pin. * Problem The IC may not be turn on in the case of a circuit in which VIN rises quickly (10 V/100 s or faster), such as that shown in figure 15. Also, the OVP latch may operate even though the FB pin is normally at VOVP or below after the IC is activated. * Reason Because of the IC circuit configuration, the timer latch block operates first. * Remedy (counter measure) Take remedial action such as configuring a time constant circuit (RB, CB) as shown in figure 16, to keep the VIN rise speed below 10 V/100 s. Also, if there is marked high-frequency noise on the VIN pin, a noise cancellation capacitor (CN) with the best possible high-frequency characteristics (such as a ceramic capacitor) should be inserted between the VIN pin and GND, and close to the VIN pin. When configuring an IC power supply with an activation resistance and backup winding, such as an AC/DC converter, the rise of VIN will normally be around 1 V/100 s, and there is no risk of this problem occurring, but careful attention must be paid to high-frequency noise. Also, this phenomenon is not occuring to the HA17384S, because OVP function is not built-in.
Input Output
VIN
VIN HA17384 Series GND Feedback
Figure 15 Example of Circuit with Fast VIN Rise Time
Rev.2, Jul. 2002, page 27 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Input Time constant circuit VIN 18V CB 1F + RB 51 VIN HA17384 Series GND CN Feedback Output
Figure 16 Sample Remedial Circuit 2. Externally Synchronized Operation * Case When, with a power supply using the HA17384S/H or HA17385H, externally synchronized operation is performed by applying an external syncronous signal to the RT/CT pin (pin 4). * Problem Synchronized operation may not be possible if the amplitude of the external syncronous signal is too large. * Reason The RT/CT pin falls to a potential lower than the ground. * Remedy (counter measure) In this case, clamping is necessary using a diode with as small a VF value as possible, such as a schottky barrier diode, as shown in figure 17.
Vref HA17384 Series RT CT 47 0.01F External synchronous signal
Figure 17 Sample Remedial Circuit
Rev.2, Jul. 2002, page 28 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Package Dimensions
As of January, 2002
Unit: mm
9.6 10.6 Max 8 5
1 0.89
4 1.3
2.54 Min 5.06 Max
1.27 Max
6.3 7.4 Max
7.62
0.5 Min
0.25 - 0.05 0 - 15
Hitachi Code JEDEC JEITA Mass (reference value)
+ 0.10
2.54 0.25
0.48 0.10
DP-8B Conforms Conforms 0.51 g
As of January, 2002
Unit: mm
4.90 5.3 Max 5 8
1
4
3.95
*0.22 0.03 0.20 0.03
1.75 Max
0.75 Max
6.10 - 0.30
+ 0.10
1.08 0 - 8
+ 0.67
+ 0.11 0.14 - 0.04
1.27
0.60 - 0.20
*0.42 0.08 0.40 0.06
0.15 0.25 M
*Dimension including the plating thickness Base material dimension Hitachi Code JEDEC JEITA Mass (reference value) FP-8DC Conforms -- 0.085 g
Rev.2, Jul. 2002, page 29 of 30
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Disclaimer
1. Hitachi neither warrants nor grants licenses of any rights of Hitachi's or any third party's patent, copyright, trademark, or other intellectual property rights for information contained in this document. Hitachi bears no responsibility for problems that may arise with third party's rights, including intellectual property rights, in connection with use of the information contained in this document. 2. Products and product specifications may be subject to change without notice. Confirm that you have received the latest product standards or specifications before final design, purchase or use. 3. Hitachi makes every attempt to ensure that its products are of high quality and reliability. However, contact Hitachi's sales office before using the product in an application that demands especially high quality and reliability or where its failure or malfunction may directly threaten human life or cause risk of bodily injury, such as aerospace, aeronautics, nuclear power, combustion control, transportation, traffic, safety equipment or medical equipment for life support. 4. Design your application so that the product is used within the ranges guaranteed by Hitachi particularly for maximum rating, operating supply voltage range, heat radiation characteristics, installation conditions and other characteristics. Hitachi bears no responsibility for failure or damage when used beyond the guaranteed ranges. Even within the guaranteed ranges, consider normally foreseeable failure rates or failure modes in semiconductor devices and employ systemic measures such as failsafes, so that the equipment incorporating Hitachi product does not cause bodily injury, fire or other consequential damage due to operation of the Hitachi product. 5. This product is not designed to be radiation resistant. 6. No one is permitted to reproduce or duplicate, in any form, the whole or part of this document without written approval from Hitachi. 7. Contact Hitachi's sales office for any questions regarding this document or Hitachi semiconductor products.
Sales Offices
Hitachi, Ltd.
Semiconductor & Integrated Circuits Nippon Bldg., 2-6-2, Ohte-machi, Chiyoda-ku, Tokyo 100-0004, Japan Tel: (03) 3270-2111 Fax: (03) 3270-5109
URL
http://www.hitachisemiconductor.com/
For further information write to:
Hitachi Semiconductor (America) Inc. 179 East Tasman Drive San Jose,CA 95134 Tel: <1> (408) 433-1990 Fax: <1>(408) 433-0223 Hitachi Europe Ltd. Electronic Components Group Whitebrook Park Lower Cookham Road Maidenhead Berkshire SL6 8YA, United Kingdom Tel: <44> (1628) 585000 Fax: <44> (1628) 585200 Hitachi Europe GmbH Electronic Components Group Dornacher Strae 3 D-85622 Feldkirchen Postfach 201, D-85619 Feldkirchen Germany Tel: <49> (89) 9 9180-0 Fax: <49> (89) 9 29 30 00 Hitachi Asia Ltd. Hitachi Tower 16 Collyer Quay #20-00 Singapore 049318 Tel : <65>-6538-6533/6538-8577 Fax : <65>-6538-6933/6538-3877 URL : http://semiconductor.hitachi.com.sg Hitachi Asia Ltd. (Taipei Branch Office) 4/F, No. 167, Tun Hwa North Road Hung-Kuo Building Taipei (105), Taiwan Tel : <886>-(2)-2718-3666 Fax : <886>-(2)-2718-8180 Telex : 23222 HAS-TP URL : http://www.hitachi.com.tw Hitachi Asia (Hong Kong) Ltd. Group III (Electronic Components) 7/F., North Tower World Finance Centre, Harbour City, Canton Road Tsim Sha Tsui, Kowloon Hong Kong Tel : <852>-2735-9218 Fax : <852>-2730-0281 URL : http://semiconductor.hitachi.com.hk
Copyright (c) Hitachi, Ltd., 2002. All rights reserved. Printed in Japan.
Colophon 6.0
Rev.2, Jul. 2002, page 30 of 30

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